Energy Storage Systems for Electrical Microgrids with Pulsed Power Loads

ABSTRACT

Pulsed power loads (PPLs) are highly non-linear and can cause significant stability and power quality issues in an electrical microgrid. According to the present invention, many of these issues can be mitigated by an Energy Storage System (ESS) that offsets the PPL. The ESS can maintain a constant bus voltage and decouple the generation sources from the PPL. For example, the ESS specifications can be obtained with an ideal, band-limited hybrid battery and flywheel system.

CROSS-REFERENCE TO RELATED APPLICATION

This application claims the benefit of U.S. Provisional Application No.62/908,732, filed Oct. 1, 2019, which is incorporated herein byreference.

STATEMENT OF GOVERNMENT INTEREST

This invention was made with Government support under Contract No.DE-NA0003525 awarded by the United States Department of Energy/NationalNuclear Security Administration. The Government has certain rights inthe invention.

FIELD OF THE INVENTION

The present invention relates to electrical microgrids and, inparticular, to energy storage systems for electrical microgrids withpulsed power loads.

BACKGROUND OF THE INVENTION

Microgrids, with new designs and implementations, are growing tointegrate various local generation capacities, as well as various typesof loads. One emerging problem is the pulsed power load (PPL), which canadd unwanted frequency content and instabilities to the bus voltage ofthe microgrid. See M. Farhadi and O. Mohammed, IEEE Trans. Smart Grid6(1), 54 (2015). These fluctuations can cause the collapse of voltageand systemwide performance degradation and affect the power and energytransfer quality of the network. In an AC or DC microgrid system, theexistence of nonlinear loads may compromise the stability of the systemduring the transients. See W. W. Weaver et al., IEEE Trans. EnergyConvers. 32(2), 820 (2017). Given a PPL's peak power, period, and dutycycle, different energy storage systems (ESS) with different capacitiesand bandwidths of operation are needed to complement the load to fulfillvoltage harmonics and noise goals, as well as control objectives.Super-capacitors, flywheels and batteries have already been used forthese purposes. See R. A. Dougal et al., IEEE Trans. Compon. Packag.Technol. 25(1), 120 (2002). In DC microgrid systems with PPLs, thegeneral approach is to decouple the load from the source by usingappropriately large ESS. See J. M. Guerrero et al., IEEE Trans. Ind.Electron. 60(4), 1263 (2013). The ESS can mitigate instability of thesystem in a constant power approach. See A. L. Gattozzi et al., “Powersystem and energy storage models for laser integration on navalplatforms,” in IEEE Electric Ship Technologies Symposium, June 2015, pp.173-180.

In a constant power load, the current is inversely proportional to thevoltage. This creates a negative incremental impedance and can lead toinstability with a pulsed power load. See R. D. Middlebrook, “Inputfilter considerations in design and application of switchingregulators,” in Proc. IEEE Industry Applications Society Annual Meeting,1976, pp. 366-382; and W. W. Weaver and P. T. Krein, IEEE Trans. PowerElectron. 24(5), 1248 (2009). Power buffers have been proposed todecouple the load from the grid and to compensate for non-linear loadtransients. See D. Logue and P. T. Krein, “The power buffer concept forutility load decoupling,” in IEEE Annual Power Electronics SpecialistsConference, vol. 2, 2000, pp. 973-978; W. W. Weaver and P. T. Krein,“Mitigation of power system collapse through active dynamic buffers,” inPower Electronics Specialists Conference, vol. 2, June 2004, pp.1080-1084; and W. W. Weaver, IEEE Trans. Power Electron. 26(3), 852(2011). Load terminal characteristics are controlled to mimic a linearbehavior. Ideally, the power buffer filters the fast dynamics of theload and decouples the load-side system from the grid-side dynamics.However, for large loads with extended transient times, a larger ESS isneeded. See R. S. Balog et al., IEEE Trans. Smart Grid 3(1), 253 (2012).

ESS devices are widely used to improve power quality and energytransfer. See Z. Yan and X. P. Zhang, IEEE Access 5, 19 373 (2017).Typically, to compensate for the slow change of load power, such as inhourly variations, storage elements with high energy densities arerequired. In contrast, for faster variations, high power density andfaster response rate devices are needed. Therefore, it is important toconsider the frequency bandwidth capabilities of the ESS. Whilesuper-capacitors are suitable for high power bandwidth operations,batteries with lower bandwidths and higher energy densities alleviatepower and energy deficiencies and extend the operating time. See Y.Zhang and Y. W. Li, IEEE Trans. Power Electron. 32(4), 2704 (2017); andT. Dragicevic et al., IEEE Trans. Power Electron. 29(2), 695 (2014).

SUMMARY OF THE INVENTION

The present invention is directed to energy storage systems (ESSs) formitigating the effects of pulsed power loads (PPLs) on an electricalmicrogrid. A local ESS control can maintain the voltage and currents ofa PPL system. As examples of the invention, ideal, band-limited andreduced-order hybrid battery and flywheel storage systems were simulatedand compared to illustrate how a proper ESS technology based on cut-offfrequency can meet bus voltage performance specifications. For the idealloss-less system, the ESS can achieve zero energy trade over each cycleof the pulsed load duty cycle. On the other hand, the internal losses inthe simulated battery and flywheel systems lead to an overall decreasein the energy of the battery and flywheel systems. For accurate sizingof the ESS it is important to account for losses. Optimization schemescan determine optimal power flow and/or optimal amount of series andparallel cells to reduce losses as well as relax the bus voltageconstraint to explore the meta-stability boundary for reducing theoverall size of the ESS.

BRIEF DESCRIPTION OF THE DRAWINGS

The detailed description will refer to the following drawings, whereinlike elements are referred to by like numbers.

FIG. 1 is a plot of a pulse width modulated waveform with period ofT_(p), duty cycle of D_(p), and peak power of P_(peak).

FIG. 2 is a pulse power load model with energy storage.

FIG. 3 is a pulse power load model with band-limited energy storage.

FIG. 4 is a graph of a first-order filter when ω_(cut-off)=100000 rad/s.

FIG. 5 is an illustration of the overall form of flywheel and batterymodels.

FIG. 6 is a flywheel model bus interface converter.

FIG. 7 is a graph of the frequency response of a flywheel system.

FIG. 8 is a battery system model with bus interface converter.

FIG. 9 is a graph of the battery system frequency response.

FIGS. 10A-10C are graphs of pulsed load and ESS powers in time andfrequency domains. FIG. 10A is for a duty cycle of 5%. FIG. 10B is for aduty cycle of 50%. FIG. 10C is for a duty cycle of 90%.

FIG. 11 is a plot of the energy storage power surface versus frequencyand duty cycle.

FIGS. 12A-12C are graphs of pulse load and energy storage currents andthe regulated load voltage. FIG. 12A is for ω_(cut-off) of 100000 rad/s.FIG. 12B is for ω_(cut-off) of 100 rad/s. FIG. 12C is for ω_(cut-off) of10 rad/s.

FIG. 13 is a graph of the pulse load voltage variation versus thestorage cut-off frequency.

FIG. 14A is a graph of the overall injected currents for a battery. FIG.14B is a graph of the overall injected currents for a flywheel system.FIG. 14C is a graph of pulsed load and hybrid storage system currents.

FIG. 15A is a graph of individual cell battery SOC. FIG. 15B is a graphflywheel RPM. FIG. 15C is a graph of pulse load voltage.

DETAILED DESCRIPTION OF THE INVENTION

The present invention is directed to an ESS system for an electricalmicrogrid with a PPL. The invention can specify the capacity andrequired frequency response capability of an aggregate ESS for a desiredbus voltage characteristic, for example, to maintain a constant DC busvoltage while the storage element supplies the high frequency content ofthe load. The invention can provide trade-offs between bus voltageharmonic content and the ESS capacity and bandwidth. From the idealbaseline design of the ESS, different ESS technologies, batteries,super-capacitors, flywheels, for example, can be fitted together tocover the response spectrum established by the baseline design of theESS.

A PPL is defined as a pulse-width modulated (PWM) waveform P(t) with aduty cycle D_(p), period T_(p), and peak value P_(peak), as shown inFIG. 1. Pulse width modulation of the power is not to be confused withthe pulse width modulation of the converter switch control. An averageload power is defined to provide a constraint for overall ESS powerflow. The ESS control objective is to maintain the load voltage and thegrid-side current flow. The required energy capacity of the ESS isdetermined from the PPL peak power, duty cycle, and periodcharacteristics. However, the quality of the maintained voltage andcurrent depend upon the ESS bandwidth. The operation of the system underideal, band-limited storage systems as well as reduced order flywheel,battery, and hybrid ESS systems are described below.

Pulsed Load System and Energy Storage Control

An example of a reduced-order model (ROM) comprising a bus interfaceconverter, pulse load (PPL), and ideal energy storage element (ESS) isshown in FIG. 2. See W. W. Weaver et al., IEEE Trans. Energy Conyers.32(2), 820 (2017). The state-space of the model is

$\begin{matrix}{{L\; \frac{{di}(t)}{dt}} = {{{- R_{L}}{i(t)}} - {v(t)} + {\lambda \; v_{b}}}} & (1) \\{{C\; \frac{{dv}(t)}{dt}} = {{i(t)} - \frac{p(t)}{v(t)} - \frac{v(t)}{R} + u}} & (2)\end{matrix}$

where u represents a current injection from the ESS and P(t) is the PPL,as shown in FIG. 1. Furthermore in (1)-(2) R_(L) represents the lineresistance, L is the inductance, C is the bus capacitance and v(t) isthe input source voltage. For the baseline analysis, the source busvoltage v_(b) and the converter duty cycle λ are assumed to be constantto isolate the ESS and pulse load. It is also assumed that the capacitorC is small so as not to affect the ESS performance. Then, u is thecurrent of a single, or aggregated, ESS.

Energy Storage Control

For the baseline, the objective for the storage element u is to supplythe necessary energy so that i and v are constant. Therefore, thesteady-state average of (1)-(2) is

$\begin{matrix}{0 = {{{- R_{L}}\overset{\_}{i}} - \overset{\_}{v} + {\lambda \; {\overset{\_}{v}}_{b}}}} & (3) \\{0 = {{- \overset{\_}{i}} - \frac{\overset{\_}{P}}{\overset{\_}{v}} - \frac{\overset{\_}{v}}{R} + u}} & (4)\end{matrix}$

where the time average load power is

$\begin{matrix}{\overset{\_}{P} = {{\frac{1}{T_{p}}{\int_{0}^{T_{p}}{{P(t)}{dt}}}} = {D_{p}{P_{peak}.}}}} & (5)\end{matrix}$

Solving (3)-(4) for the average voltage and current, v and ī yields

$\begin{matrix}{\overset{\_}{v} = \frac{\sqrt{R( {{\lambda^{2}{\overset{\_}{v}}_{b}^{2}} - {4R_{L}D_{p}{P_{peak}( {R + R_{L}} )}}} )} + {{\lambda R}{\overset{\_}{v}}_{b}}}{2( {R + R_{L}} )}} & (6) \\{\overset{\_}{i} = \frac{{\lambda {{\overset{\_}{v}}_{b}( {R + {2R_{L}}} )}} - \sqrt{R( {{\lambda^{2}R{\overset{\_}{v}}_{b}^{2}} - {4R_{L}D_{p}{P_{peak}( {R + R_{L}} )}}} )}}{2{R_{L}( {R + R_{L}} )}}} & (7)\end{matrix}$

Then, the current from the ESS is

$\begin{matrix}{u = \frac{2( {R + R_{L}} )( {{D_{p}P_{peak}} - {P(t)}} )}{\sqrt{R( {{\lambda^{2}{Rv}_{b}^{2}} - {4R_{L}D_{p}{P_{peak}( {R + R_{L}} )}}} )} + {\lambda Rv}_{b}}} & (8)\end{matrix}$

The power from the storage device is then

P _(u)(t)=v _(u) =P(t)−D _(p) P _(peak).  (9)

Integrating the storage power over the period of positive power outputyields

$\begin{matrix}\begin{matrix}{W_{u} = {{\int_{0}^{T_{p}}{{P_{u}(t)}{dt}}} = {\int_{0}^{T_{p}}{( {{P(t)} - {D_{p}P_{peak}}} ){dt}}}}} \\{= {\int_{0}^{D_{p}T_{p}}{( {P_{peak} - {D_{p}P_{peak}}} ){dt}}}} \\{= {\int_{0}^{D_{p}T_{p}}{( {P_{peak}( {1 - D_{p}} )} ){dt}}}} \\{= {{- ( {D_{p} - 1} )}D_{p}T_{p}P_{peak}}}\end{matrix} & (10)\end{matrix}$

where W_(u) is the baseline total energy storage capacity of the ESS.

The total energy supplied from the ESS element u, over the period T_(p),is zero. Then the ESS control law (8) is derived from the average powerin (5). If losses in the ESS are considered, (9) can be modified andcombined with (5) to compensate. However, losses are neglected hereinsince this description is primarily focused on the baseline terminalcharacteristics of the ESS.

The maximum of (10) over one load cycle is found from

$\begin{matrix}{\frac{{dW}_{u}}{{dD}_{p}} = \begin{matrix}{0 = {{T_{p}P_{peak}} - {2D_{p}T_{p}P_{peak}}}} \\{= {T_{p}{{P_{peak}( {1 - {2D_{p}}} )}.}}}\end{matrix}} & (11)\end{matrix}$

Hence, the maximum required ESS storage capacity is when D_(p)=½.

Linear Methods for Stability Bounds

For small-signal stability analysis the linear model of the form

{hacek over (x)}=Ax+Bu,  (12)

is used. The small-signal A matrix for (1)-(2) is

$\begin{matrix}{A = {\begin{bmatrix}{- \frac{R_{L}}{L}} & {- \frac{1}{L}} \\\frac{1}{C} & \frac{\frac{D_{p}P_{peak}}{v_{o}^{2}} - \frac{1}{R}}{C}\end{bmatrix}.}} & (13)\end{matrix}$

The characteristic equation of (12) with (13) is

$\begin{matrix}{{s^{2} + {s( {\frac{1}{CR} + \frac{R_{L}}{L} - \frac{D_{p}P_{peak}}{{Cv}_{o}^{2}}} )} + ( {\frac{R_{L}}{CLR} + \frac{1}{CL} - \frac{R_{L}D_{p}P_{peak}}{{CLv}_{o}^{2}}} )} = 0.} & (14)\end{matrix}$

For stability, the terms of (14) should be

$\begin{matrix}{{{\frac{R_{L}}{CLR} + \frac{1}{CL} - \frac{R_{L}D_{p}P_{peak}}{{CLv}_{0}^{2}}} = {\frac{1 + {R_{L}( {\frac{1}{R} - \frac{D_{p}P_{peak}}{v_{o}^{2}}} )}}{CL} > 0}}\;} & (15) \\{and} & \; \\{{{- \frac{D_{p}P_{peak}}{{Cv}^{2}}} + \frac{1}{CR} + \frac{R_{L}}{L}} = {{\frac{\frac{1}{R} - \frac{D_{p}P_{peak}}{v_{o}^{2}}}{C} + \frac{R_{L}}{L}} > 0.}} & (16)\end{matrix}$

Then, the system is stable if

$\begin{matrix}{{0 < R \leq \frac{v_{o}^{2}}{D_{p}P_{peak}}},} & (17)\end{matrix}$

where

$\frac{v_{o}^{2}}{D_{p}P_{peak}}$

is the equivalent average impedance of the pulse load. The aboveinequality implies if the resistive load R dissipates more power thanthe average pulse load, then it is stable. However, if this is not thecase and R is

$\begin{matrix}{R > \frac{v_{o}^{2}}{D_{p}P_{peak}}} & (18)\end{matrix}$

then the system is stable if the inductance and series inductorresistance are chosen such that

$\begin{matrix}{0 < L < \frac{{CR}^{2}v_{o}^{4}}{( {v_{o}^{2} - {{RD}_{p}P_{peak}}} )^{2}}} & (19) \\{\frac{L( {{{RD}_{p}P_{peak}} - v_{o}^{2}} }{{CRv}_{o}^{2}} < R_{L} < {\frac{{Rv}_{o}^{2}}{{{RD}_{p}P_{peak}} - v_{o}^{2}}.}} & (20)\end{matrix}$

In (20) the series resistance R_(L) must be less than the total loadimpedance which is equivalent to impedance matching for maximum powertransfer. The equivalent parallel impedance is

$\begin{matrix}{{{\frac{v_{o}^{2}}{D_{p}P_{peak}}//R} = {\frac{{Rv}_{o}^{2}}{{{RD}_{p}P_{peak}} + v_{o}^{2}} > R_{L}}},} & (21)\end{matrix}$

which is the upper constraint on R_(L).

Energy Storage Frequency Content

Any periodic function, linear or nonlinear, can be represented as aFourier series. The Fourier series of a PWM function is

$\begin{matrix}{{{f_{PWM}(t)} = {D_{p} + {\frac{2}{}{\sum\limits_{n = 1}^{\infty}\; {\frac{\sin ( {nD}_{p} )}{n}{\cos ( {n\frac{2}{T_{p}}t} )}}}}}},} & (22)\end{matrix}$

where D_(p) is the duty cycle, T_(p) is the period, and the magnitude ofthe pulse is unity. The frequency content of the PWM pulse load signalis then

$\begin{matrix}{{P(t)} = {{P_{peak}( {D_{p} + {\frac{2}{}{\sum\limits_{n = 1}^{\infty}\; {\frac{\sin ( {nD}_{p} )}{n}{\cos ( {n\frac{2}{T_{p}}t} )}}}}} )}.}} & (23)\end{matrix}$

The ESS ideally only provides the AC content of the signal and the DC isprovided by the source(s). The frequency content of storage device poweris then

$\begin{matrix}\begin{matrix}{{P_{u}(t)} = {{P\text{(t)}} = {D_{p}P_{peak}}}} \\{= {P_{peak}\frac{2}{}{\sum\limits_{n = 1}^{\infty}\; {\frac{\sin ( {nD}_{p} )}{n}{{\cos ( {n\frac{2}{T_{p}}t} )}.}}}}}\end{matrix} & (24)\end{matrix}$

From (8) and (24), the storage device current is

$\begin{matrix}{\mspace{20mu} {u = {{\frac{2( {R + R_{L}} )( {P_{peak}\frac{2}{\pi}{\sum\limits_{n = 1}^{\infty}{\frac{\sin ( {n\; \pi \; D_{p}} )}{n}{\cos ( {n\; \frac{2\pi}{T_{p}}t} )}}}} )}{\sqrt{R( {{\lambda^{2}{Rv}_{b}^{2}} - {4R_{L}D_{p}{P_{peak}( {R + R_{L}} )}}} )} + {\lambda \; {Rv}_{\text{?}}}}.\text{?}}\text{indicates text missing or illegible when filed}}}} & (25)\end{matrix}$

The ESS current injection in (25) is the baseline reference signal suchthat the load voltage remains constant and the source only supplies theaverage power. For any other choice or implementation of an ESS otherthan (25), there will be harmonic content on the bus voltage and in thesource power. It should also be noted that (25) is an infinite sum,which implies any real ESS (which is band-limited) will not be able tomeet the baseline. As described below, band-limited storage devices inideal form as well as reduced-order flywheel and battery models can bespecified for the system.

Band-Limited ESS

The operational bandwidth of any real ESS devices is limited. Ingeneral, the ESS can be modeled as a Low Pass Filter (LPF). See Z. Yanand X. P. Zhang, IEEE Access 5, 19 373 (2017); and V. Yuhimenko et al.,IEEE J. Emerg. Sel. Topics Power Electron. 3(4), 1001 (2015). Thecut-off frequency of this LPF depends on the ESS technology, control andother specifications. However, a generic ESS can be modeled as an LPFdescribed as

$\begin{matrix}{\frac{{du}_{f}}{dt} = {\omega_{{cut}\text{-}{off}}( {u - u_{f}} )}} & (26)\end{matrix}$

where u is the ESS control reference command, u_(f) is the injectedcurrent and ω_(cut-off) is the cut-off frequency, as shown in FIG. 3.FIG. 4 demonstrates the gain versus the frequency of (26) whenω_(cut-off)=100000 rad/s. Flywheel and battery system models for theband-limited ESS are described below. The flywheel and battery devicesare used to meet the ESS bandwidth and capacity requirements,respectively. For both devices, the overall topology is as shown in FIG.5. Other EES technologies are also shown below to have similarresponses.

Flywheel System and Control

A generalized reduced-order flywheel energy storage model is shown inFIG. 6. The flywheel system descriptions and parameters for areduced-order flywheel device are given in Table. I. This simplifiedmodel contains a spinning mass flywheel, Permanent Magnet (PM) DCmachine, and a DC-DC converter to interface with the load bus.

TABLE I FLYWHEEL CELL SYSTEM AND CONTROL PARAMETERS ParameterDescription Value Flywheel System Parameters J_(f) Moment of Inertia0.018 Kg m² k_(t) Torque Constant 1 Nm/A R_(pm) Armature Resistance 0.05Ω L_(pm) Armature Inductance 10 mH C_(u) Converter Capacitance 1000 μFR_(Cu) Converter Resistance 10 KΩ L_(u) Line Inductance 10 mH R_(u) LineResistance 0.01 Ω B Windage Friction Coefficient$0.001\mspace{14mu} {{Nm}/\frac{rad}{s}}$ Control Gains k_(i) Buscurrent integral gain 10 k_(p) Bus current proportional gain  1

Simplifying assumptions for this analysis include switching effects areignored and the converter model is average mode with control input dutycycle λ_(u). Typically, the machine would be a 3-phase induction machineor switched reluctance machine, but a PMDC model is used for thisexample. Then, the minimum speed of the flywheel to support a busvoltage yields

e _(pm) =k _(t)ω_(f)(t)≥v _(bus) ,∀t.  (27)

Therefore, a buck converter in current source mode, shown in FIG. 6, canbe used as the bus interface. The energy stored in the flywheel is

W _(f)=½J _(f)ω_(f)(t)².  (28)

Hence, the minimum energy stored in the device is

$\begin{matrix}{W_{f,{m\; i\; n}} = {\frac{1}{2}{{J_{f}( \frac{v_{bus}}{k_{t}} )}^{2}.}}} & (29)\end{matrix}$

The overall power losses in the device are

$\begin{matrix}{{P_{loss}(t)} = {{R_{p\; m}{i_{p\; m}^{2}(t)}} + {R_{Lu}{i_{u}^{2}(t)}} + \frac{v_{u}^{2}(t)}{R_{Cu}} + {B\; {{\omega_{f}^{2}(t)}.}}}} & (30)\end{matrix}$

The electrical torque and speed voltage of the PMDC machine areτ_(pm)=k_(t)i_(pm)(t) and e_(pm)=k_(t)ω_(f)(t) respectively. The overallflywheel state-space model is

$\begin{matrix}{{J_{f}\frac{d\; \omega_{f}}{dt}} = {{{- B}\; {\omega_{f}(t)}} - {k_{t}{i_{p\; m}(t)}}}} & (31) \\{{L_{p\; m}\frac{{di}_{p\; m}}{dt}} = {{k_{t}{\omega_{f}(t)}} - {R_{{pm}\;}{i_{p\; m}(t)}} - {v_{u}(t)}}} & (32) \\{{C_{u}\frac{{dv}_{u}}{dt}} = {{- \frac{v_{u}(t)}{R_{Cu}}} + {i_{p\; m}(t)} - {\lambda_{u}{i_{u}(t)}}}} & (33) \\{{L_{u}\frac{{di}_{u}}{dt}} = {{- u_{bus}} - {R_{Lu}{i_{u}(t)}} + {\lambda_{u}{{v_{u}(t)}.}}}} & (34)\end{matrix}$

The injected current from this ESS is required to track the ESS controllaw (8). A simple PI control can be used to enforce the referencecurrent command such that the error value is

$\begin{matrix}{e_{p} = {{i_{u,{ref}}(t)} - {i_{u}(t)}}} & (35) \\{\frac{{de}_{i}}{dt} = e_{p}} & (36) \\{\lambda_{u} = {{k_{i}e_{i}} + {k_{p}e_{p}}}} & (37) \\{0 \leq \lambda_{u} \leq 1.} & (38)\end{matrix}$

As shown in FIG. 6, the controller attempts to minimize the error e_(p)over time by adjustment of the control variable λ_(u). The effectivenessof the current tracking depends on the response of the system. Theoverall frequency response for the band-limited flywheel storage systemin (31)-(34) with its control in (35)-(38) is shown in FIG. 7.

Battery System and Control

A generalized reduced-order battery and converter model is shown in FIG.8. See K. Khan et al., IET Elect. Syst. Transport. 8(3), 197 (2018).Relevant system parameter descriptions are presented in Table II. Inthis model the converter is an average mode model with control inputduty cycle λ_(u), and v_(batt)<v_(bus). R_(c1) is very large and R_(c2)is small.

TABLE II BATTERY CELL SYSTEM PARAMETERS Parameter Description ValueV_(oc) Open Circuit Voltage 48 V Q Max charge capacity 10 A · Hr C₁Electrochemical Polarization Capacitance 750 F R_(c1) ElectrochemicalPolarization Resistance 10 KΩ L Equivalent Series Inductance 0.17 μH REquivalent Series Resistance 0.31 Ω C₂ Concentration PolarizationCapacitance 400 F R

₂ Concentration Polarization Resistance 0.24 mΩ C

Converter Capacitance 10 μF R_(Cu) Converter Resistance 1 KΩ L

Line Inductance 10 mH R

Line Resistance 0.1 Ω Control Gains k

Bus current integral gain 300 k

Bus current proportional gain 20 k

Battery current integral gain 1000 k

Battery current proportional gain 100

indicates data missing or illegible when filedThe energy discharged from the battery is measured in terms of the sumof charge provided over some period as

$\begin{matrix}{{A\; h} = {\frac{\int_{0}^{t}{{i_{batt}(\tau)}d\; \tau}}{3600\; \frac{s}{hr}}.}} & (39)\end{matrix}$

A battery has a maximum storage capacity (Ah)_(capacity). TheState-of-Charge (SOC) of the battery is calculated as

$\begin{matrix}{{{SOC}(\%)} = {100\; \frac{( {A\; h} )_{capacity} - {A\; h}}{( {A\; h} )_{capacity}\;}}} & (40)\end{matrix}$

where SOC of 100% and 0% denote fully charged and fully dischargedbattery storage, respectively. The energy stored in the battery is

W _(c)(t)=½Cv _(c) ²(t)  (41)

where C is the equivalent bulk capacitance of the battery. The energyavailable in the battery is

$\begin{matrix}{\mspace{20mu} {Q = {{\frac{1}{3600}{\int{{i_{batt}(t)}{dt}}}} = {{\frac{{Cv}_{\text{?}}}{3600}.\text{?}}\text{indicates text missing or illegible when filed}}}}} & (42)\end{matrix}$

The SOC of the battery is found from

$\begin{matrix}{\mspace{20mu} {{SOC} = {{\frac{Q - \frac{{Cv}_{\text{?}}}{3600}}{Q}.\text{?}}\text{indicates text missing or illegible when filed}}}} & (43)\end{matrix}$

The battery losses are

$\begin{matrix}{P_{loss} = {{{i_{batt}^{2}(t)}R_{batt}} + \frac{v_{c\; 1}^{2}(t)}{R_{c\; 1}} + {\frac{v_{c\; 2}^{2}(t)}{R_{c\; 2}}.}}} & (44)\end{matrix}$

The state-space model of the battery storage system in FIG. 8 is

$\begin{matrix}{{C_{1}\frac{{dv}_{c\; 1}}{dt}} = {{- i_{batt}} - \frac{v_{c\; 1}}{R_{c\; 1}}}} & (45) \\{{L_{1}\frac{{di}_{batt}}{dt}} = {{{- R_{1}}{i_{batt}(t)}} + {v_{c\; 1}(t)} + {v_{c\; 2}(t)} + V_{a\; c} - {\lambda_{u}{v_{u}(t)}}}} & (46) \\{{C_{2}\frac{{dv}_{c\; 2}}{dt}} = {{- {i_{batt}(t)}} - \frac{v_{c\; 2}}{R_{2}}}} & (47) \\{{C_{u}\frac{{dv}_{u}}{dt}} = {{\lambda \; {i_{batt}(t)}} - \frac{v_{u}(t)}{R_{Cu}} - {i_{u}(t)}}} & (48) \\{{L_{u}\frac{{di}_{u}}{dt}} = {{- v_{bus}} - {R_{Lu}{i_{u}(t)}} + {{v_{u}(t)}.}}} & (49)\end{matrix}$

The control of the boost converter can be obtained from two nested PIloops

$\begin{matrix}{e_{p} = {{i_{u,{ref}}(t)} - {i_{u}(t)}}} & (50) \\{\frac{{de}_{i}}{dt} = e_{p}} & (51) \\{i_{{batt},{ref}} = {{k_{i,u}e_{i}} + {k_{p,u}e_{p}}}} & (52) \\{e_{p,{batt}} = {{i_{{batt},{ref}}(t)} - {i_{batt}(t)}}} & (53) \\{\frac{{de}_{i,{batt}}}{dt} = e_{p,{batt}}} & (54) \\{\lambda_{u} = {{{- k_{i,{batt}}}e_{i,{batt}}} - {k_{p}e_{p,{batt}}} + 1}} & (55) \\{{0 \leq \lambda_{u} \leq 1},} & (56)\end{matrix}$

where the inner loop controls the battery current i_(batt) and the outerloop controls the bus injection current i_(u), as shown in FIG. 8. Thelow pass filter representation of the battery system with its control isdemonstrated in FIG. 9.

Hybrid Battery and Flywheel System

Battery and flywheel hybrid storage systems have been widely used totake advantage of the battery energy density and the flywheel's higherresponse rate and power density. See S. Vazquez et al., IEEE Trans. Ind.Electron. 57(12), 3881 (2010); and L. Gauchia et al., “New approach tosupercapacitor testing and dynamic modelling,” in IEEE Vehicle Power andPropulsion Conference, September 2010, pp. 1-5. Here, the hybrid systemconsists of a parallel battery and flywheel configuration. The batterysystem is considered as the primary low frequency ESS and the flywheelsystem compensates at higher frequencies. The reference signals forindividual flywheel and battery cells are

$\begin{matrix}{i_{{fw},{ref}} = \frac{i_{u,{ref},{total}} - {i_{u,{batt},{meas}}N_{p,{batt}}}}{N_{p,{fw}}}} & (57) \\{i_{{batt},{ref}} = \frac{i_{u,{ref},{total}}}{N_{p,{batt}}}} & (58)\end{matrix}$

where N_(p,batt) and N_(p,fw) are the number parallel cells for batteryand flywheel systems, respectively. The reference current isi_(u,ref,total) for the overall hybrid system, and i_(u,batt,meas) isthe measured current injected by the overall battery storage system.

Examples

Three examples of the invention are described below. First, a numericexample presents the behavior of the pulse load system from FIG. 2 whenthe ESS is controlled according to (25). The second example presents thecase when the storage system is a generic band-limited ESS as shown inFIG. 3. The third example demonstrates the pulse load system behaviorwhen the baseline ESS is replaced by band limited combination of batteryand flywheel storage systems. For this hybrid system, the battery andflywheel systems each comprise series and parallel cells so that theycan support the load voltage level as well as the requested current. Forthis hybrid case, the parameters are given in Tables I and IIcorresponding to FIG. 6 and FIG. 8, respectively.

The parameters for the hybrid storage are chosen such that the overallstorage meets the minimum requirements given in (10). As describedabove, the control law in (8) accounts only for loss-less ESS. Thisimplies that if an auxiliary energy source is not available over afinite amount of time, the battery and flywheel elements will loseenergy (proportional to (30) and (44)) to a point that they cannotsupport the system current defined by (8). The considerations forcontrol of lossy storage systems can bring about several optimizationpaths. However, here the capacity of the storage system is chosen sothat the storage system can sustain the load for sufficiently longperiods of time.

The bandwidths of operation for battery and flywheel systems also dependon their respective control gains. For this example, some reasonablecontrol gains (shown in Tables I and II) are chosen so that the inherentbandwidths of each storage type are not significantly affected.

Frequency Content of Baseline ESS

As shown in FIGS. 10A-10C, as the load duty cycle increases, there ismore low frequency content to the power signal. This is expected sincethe duty cycle D_(p) also represents the average of the signal. The mostsignificant feature of the ESS control is that the overall energy tradewith the ESS element is zero. When the duty cycle is 0.5 (FIG. 10B), itcan be observed that the maximum energy is requested from the storagesystem hence, verifies (11). FIG. 11 shows the entire design andspecification space for the frequency spectrum of the baseline ESS powerversus the duty cycle and the frequency of a PPL.

Pulse Load System with Generalized Band-limited Storage

FIGS. 12A, 12B, and 12C present the load current and the ESS injectedcurrent for when the cut-off frequency is 100000 (rad/s), 100 (rad/s),and 10 (rad/s), respectively. It can be seen that as the storage elementbecomes more limited in frequency response, the voltage regulationsuffers. This is because the system with lower (0 cut-off is not able totrack the baseline ESS control signal as effectively as a system withhigher bandwidth of operation. The voltage variation versus the storagecut-off frequency (ω_(cut-off) from (26)) is shown in FIG. 13. The plotin FIG. 13 represents an ESS technology selection and design tool tounderstand the resulting bus voltage variations versus the ESS cut-offresponse.

Pulse Load with Battery and Flywheel Hybrid Storage

In this example, a series and parallel battery and flywheel systems areselected to represent the band-limited ESS. To support the load currentand voltage, the battery system comprises 10 parallel and 12 seriesidentical cells. Similarly, the flywheel system comprises 3 parallel and8 series identical cells. FIGS. 14A and 14B shows the overall injectedcurrent by the hybrid battery and flywheel systems, respectively. Here,the battery supplies the majority of the power. This sharing of power isset by (58)-(57). FIG. 14C shows the overall current for the hybridstorage and the pulse load system. FIGS. 15A and 15B show individualbattery SOC and flywheel RPM, respectively. Here, the overall energy ofindividual cells decreases. However, this change is not monotonic, andthe cells recharge when the instantaneous load power is more than theaverage. FIG. 15C shows the load voltage and variations due to thechoice in ESS technologies and their resulting response limits. Theamount of voltage variation is comparable to the results obtained inFIGS. 12 and 13.

The present invention has been described as energy storage systems forelectrical microgrids with pulsed power loads. It will be understoodthat the above description is merely illustrative of the applications ofthe principles of the present invention, the scope of which is to bedetermined by the claims viewed in light of the specification. Othervariants and modifications of the invention will be apparent to those ofskill in the art.

We claim:
 1. An electrical microgrid, comprising a pulsed power loadthat provides a load transient to a bus of the electrical microgrid, abus interface converter having a control input duty cycle that providesan injected current at the bus, an energy storage system that injects acurrent to the bus interface converter, and a controller that adjuststhe control input duty cycle of the bus interface converter to controlthe injected current at the bus so as to mitigate the load transientfrom the pulsed power load and maintain a desired load voltage at thebus.
 2. The electrical microgrid of claim 1, wherein energy storagesystem has a baseline energy storage capacity ofW_(u)=−(D_(p)−1)D_(p)T_(p)P_(peak), where D_(p) is a duty cycle, T_(p)is a period, and P_(peak) is a peak value of the pulsed power load. 3.The electrical microgrid of claim 1, wherein the injected current is$u = {- \frac{2( {R + R_{L}} )( {{D_{P}P_{peak}} - {P(t)}} )}{\sqrt{R( {{\lambda^{2}Rv_{b}^{2}} - {4R_{L}D_{p}{P_{peak}( {R + R_{L}} )}}} )} + {\lambda Rv_{b}}}}$where R is the converter resistance, R_(L) is the line resistance, λ isthe control input duty cycle, D_(p) is the duty cycle, P_(peak) is thepeak value, and P(t) is the time-varying power of the pulsed power load,and v_(b) is the bus voltage.
 4. The electrical microgrid of claim 1,wherein the energy storage system comprises at least one of asupercapacitor, flywheel, or battery.
 5. The electrical microgrid ofclaim 4, wherein the flywheel acts as a low-pass filter with ahigh-frequency cut-off.
 6. The electrical microgrid of claim 4, whereinthe battery acts as a low-pass filter with a low-frequency cut-off. 7.The electrical microgrid of claim 4, wherein the energy storage systemcomprises a hybrid battery and flywheel configuration.
 8. The electricalmicrogrid of claim 1, wherein the energy storage system comprises aspinning mass flywheel and a permanent magnet DC machine and the businterface converter comprises a buck converter.
 9. The electricalmicrogrid of claim 1, wherein the energy storage system comprises abattery and the bus interface converter comprises a boost converter. 10.The electrical microgrid of claim 1, wherein the energy storage systemacts as a low-pass filter that decouples a high-frequency portion of theload transient from the bus.
 11. The electrical microgrid of claim 1,wherein the energy storage system has a cut-off frequency and thecut-off frequency is sufficiently high to maintain a constant regulatedload voltage.